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13.8 V / 15 A from a PC Power Supply

2010-03-02T23:02:00.001+07:00

Safety Instructions

Caution mortal danger: The following circuit
operates at a mains voltage of 230 Vac. Because of rectification some of the
components conduct dc voltage, of more than 322 V. Work has to be carried out
only when the circuit is disconnected from the mains, and de-energized. Note
that capacitors located on the primary side, can be charged with high voltage
for several seconds.Even after switching off the mains voltage.

The major disadvantages of usual linear power supplies are high power
dissipation, the size, and the appropriated weight. When looking for an
alternative solution, I decided to use a switch mode power supply (SMPS). The
efficiency of such power supplies is around 70 % to 90 % at a power density of
0.2 W / cm³. Because homebrewing was out of the question due to lack of
time, I tried the modification of a PC switch mode power supply. The latter are
mass produced goods, and available for less than 50 DM.

Fig.1: Block diagram of a primary switching power supply

Brief description of PC SMPS Features

Depending on the PC model, these are rated anywhere between 150 and 300 W.
For supplying socket 7 main boards they have four different output voltages of
+5 V, +12 V, -12 V and -5 V. They are mainly primary switching power supplies
with power switches arranged in a half-bridge configuration. The outputs can
drive the usual 20 A (+5 V), 8 A (+12 V) and 0.5 A (-12 V, -5 V). At approx.
205 W output power and a typical efficiency of 75 % this means a dissipation of
only 68 W. I had acquired an unbranded PC power supply, measuring 140W x 100D x
50H mm, and weighing 350 g. Most power supply units are designed according to
the same principle (half-bridge configuration), and hence the following
described modification should be applicable also, to power supplies from other
manufacturers.

Fig.2: Half-bridge configuration of power switches

Regulation

After switching on the mains voltage the circuit operates
for a short duration as a free-running oscillator. This behavior is caused by a
feedback winding at the output transformer T2. As soon as the auxiliary voltage
Uaux is present, the pulse width modulator IC, TL494CN from Texas-Instruments
takes over the control function, and synchronizes the "oscillator".

The error amplifier in the TL494 compares the voltage at the +5 V output
(actual value), with a reference voltage (set value).It calculates the analogue
control variable according to the PI algorithm, and adjusts the pulse width
modulator (see Fig. 6). The modulator sends alternate pulses to the driver
transistors Q5 and Q6. The pulse duration is inversely proportional to the
variable control setting. Increased loading on the +5 V output, makes for wider
pulses. Lighter loading causes narrower pulses. As there is a finite minimum
pulse width, a minimum load of 0.1 A is required. Without this load the power
supply may be destroyed. The switching frequency is approximately 33 kHz.
fairly normal for PC power supplies. It is defined by a resistor, and a
capacitor located at pin 5 and 6 of IC1.

Fig. 3: Primary side mains filter, rectifier, power
switches and drivers

Monitoring Circuit

Several protection circuits are included in the original power supply.
Excessive primary current due to a very high secondary current, leads to a high
alternating voltage at the T3 output. If this voltage is above a fixed
threshold, the TL494 stops cyclically generating pulses, and changes to the
intermittent mode (on / off). The circuit and the load are protected likewise
against over-voltage at the +5 V output, or short-circuit at the -12 V and -5 V
outputs. Switching off is executed via H-signal to the IC1 protection input
(pin 4) as well.

If you see a KA7500 or IR3MO2 PWM regulator IC on the board, each one is a pin
compatible second source to the TL494CN. IC3 is a LM339 dual comparator type.
Some power supplies are not equipped with this IC, but instead, with a discreet
two transistor monitoring circuit, offering the same functionality.

Mods to the Secondary Rectification

The intent is for all of the available power at the 12 V
secondary of T1 to be rectified, regulated, protected, and filtered to provide
a single output of 13.8 V DC at 205 W, or more, if possible. A first check
indicated that the +12 V wire was of the same diameter as the +5 V wire.

First unsolder, and remove all components on the secondary side of T1, which
are provided for rectification, filtering, and regulation of the four output
voltages. On that part of the board, there are only three remaining components.
RC1 to RC3, and the components for providing the auxiliary power supply Uaux.

Fig.4: Secondary rectification as found in the original PC power
supply

Reconstruction of the secondary side.

Break the PCB tracks between the RC members RC1 / RC2 and both 5 V taps of
the T1 secondary winding.

Modify L4 for 12 V at 20 A. Remove windings L4a, L4b and L4c from the
toroid (counting turns of L4c). Rewind the toroid L4* with a single winding,
turn count as old L4c but with 2.5 times the thickness. Take two wires with 1
mm diameter each, bifilar wounded.

Install two low ESR electrolytic capacitors of 2200 uF each and the 100 Ohm
bleeder resistor as permanent load.

Use the old PCB tracks from the +5 V section and GND tracks as terminals
for L4*. The 100 Ohm resistor and the two 2200 uF capacitors. Insert L4* at the
same place, onto the PCB component side where the L4b winding was connected
before.

The original cooling of the rectifier diode D5 is insufficient. Adequate
cooling is achieved by a finned heat sink measuring 70 x 50 x 30 mm (W, D, H)
instead of the old aluminium sheet metal.

Fasten D5 to the heat sink and extend the three leads by 40 mm long wires.
Use isolation material and thermal compound. D5 carries on some boards the
abbreviation SKD.

Place the finned heat sink approx. 40 mm above the "stripped"
secondary (see photo) with plastic spacers and long M3 screws (avoid
short-circuit to common).

Connect the anode leads of D5a and D5b with one RC member RC1 / RC2 each.
The cathodes have to be connected to the nodal point of RC1, RC2 and L4.

Establish two links between the 12 V terminals of T1 and the RC members by
two thick wires. D5 will be fed from the 12 V winding.

A simple and clear structure of the secondary rectification was achieved
after "stripping" and "reconstruction".

Fig. 5: New designed secondary for Ua = 13,8 V

Mods to the Regulation and Protection Circuit

The part of the circuit responsible for regulation and monitoring has to be
modified at three places. Arrange additional components free standing on the
component side of the PCB.

R24* is calculated for 13.8 V output voltage. The voltage at the (+) input
of the error amplifier must be equal to 2.5 V after control loop stabilization,
i.e. half the 5 V reference voltage when the output is at 13.8 V.

R24* = 20 kOhm = 2 x 10 kOhm in series

Arrange a second universal diode 1N4148 and a 8,2 V Zener diode in series
to D16.

Usum = 8,2 V + 2 x 0,7 V = 9,6
V

Simplify the voltage divider (R36, R42, R45 and D14) in the short-circuit
protection circuit. For this remove R36 and D14. Connect the free end of R42 to
common (GND) and replace R45 with one of higher value to ensure no shut-down at
normal operation. The voltage across R42 must be less than 1,7 V (I chose 1,2
V).

R45* = 15 kOhm

The areas marked with dotted frames, show the modified or additional
components that are necessary for 13.8 V output.

Fig. 6: Regulation and protection circuits incl. all modifications

Further Modifications

After commissioning the modified board, the situation in regards to
interference looks very bad. The whole reception range from 3.5 MHz to 30 MHz
was disturbed by harmonics of the 33 kHz switching frequency. S-meter readings
showed S5 on 80 m down to S2 on 10 m. As I was testing the board in a metal
box, the HF radiation could only get out on the mains cable and/or DC output
leads. The insertion of an additional standard 230 VAC mains filter, and a
home-brewed pi-filter in the output rendered the interference inaudible.

Insert an additional 230V / 2A mains filter to the primary side, close to
the place where the mains cable enters the enclosure rear wall.

Insert a 20 A pi-filter to the DC output , behind the +/- DC terminals at
the rear wall.

The power supply enclosure must absolutely consist of iron sheet metal to
screen magnetic fields. Aluminum plates protect only against electrical fields.

Optional on the primary: Replace the 220 uF smoothing capacitors C1 and C2
by 470 uF capacitors. This reduces primary ripple, which helps output
regulation at full load.

Testing the Power Supply

Phase 1: These tests have to be carried out at a low DC
supply voltage in order to avoid component destruction in case of possible
errors. The 13.8 V output is loaded with a 12 V / 50 W car headlight globe, and
a 15 V / 1 A lab power supply is connected to GND, and Uaux. The TL494 IC
generates control pulses, with a maximum pulse duration. Check the signals at
Q5 and Q6.

Phase 2: During the second test phase, the galvanic isolated
primary side of the circuit is supplied by the lab supply also. For this
purpose make a short cable link between Uaux and U+ as well as between GND and
U-. The PWM controller tries to offer 13.8 V at the output at maximum pulse
duration. The latter cannot be successful, due to the low 15 Vdc input voltage,
and the present transformer ratio. With an oscilloscope, measured signals at
the measuring points TP1 (emitter Q1 against emitter Q2) and TP2 (cathode D5
against GND) must look like that, shown in figure 7.

Fig. 7: Signal shape at TP1 and TP2

Phase 3: Nor disconnect the lab supply from the primary side only. Instead
connect a 48 V / 1 A mains transformer to the L1 and N terminal in order to
feed the board with a galvanic isolated Ac voltage. 60 Vdc at C1 and C2 is in
Europe defined as a non-dangerous voltage rate. 48 VAC at the input causes a
rise of the output voltage up to +6 V.

If everything is all right up to now, one can proceed with the exciting test
at 230 Vac. The laboratory power supply, the 48 V transformer, the measuring
instruments and all provisional cable links attached for the test etc. must
obviously be removed. The car lamp, is further needed as a load, and for the
functional checks. If after application of the 230 Vac mains voltage, the lamps
light up brightly, the output voltage amounts to 13.8 V, and no undefined
noises, or smells are noticeable, you have won the first round. If a non
recognisable error has passed the pre-testing, the two switching transistors,
and copper tracks say good-bye, with a more or less loud bang.

For the following load test, some high power resistors with 1 Ohm
resistance, and sufficent power rating are required. The current flowing with
this load should not cause excessive heating of the rectifier diode, and the
switching transistors during a 5 minute test period.

Warning: Check temperature of components only if the
mains voltage is switched off

Cooling of the switching transistors Q1 and Q 2 at a continuous current of
15 A has to be proved in any case. When exchanging the small heat sinks, note
that they form an electrical connection between copper tracks on some boards.
Replace the missing connection by wire links. As one can see on the photo, I
did not take this measure, for further power improvement.

Operation Experience

The modified board was permanently installed in the SP120
speaker cabinet that matches my transceiver. The mains lead exit from its rear,
which also carries the DC terminals, an on-off switch, the additional mains
filter and a small 12 V blower. A green LED power-on indicator was inserted in
the front panel into a 5 mm hole. I had installed the small blower just in
case, but found it superfluous. At the low duty cycle of CW and SSB, none of
the components are getting hot. The power supply has been in use for several
years, and has given no problems.

Fig. 8: Modified power supply board in the SP120 speaker
cabinet

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13.8 V / 15 A from a PC Power Supply